Driver calibration methods and circuits

ABSTRACT

Described are amplifiers that facilitate high-speed communication with calibrated drive strength and termination impedance. Drivers and termination elements can be divided into a number N of parallel portions, one or more of which can be disabled and updated without interfering with signal (e.g., clock or data) transmission. Some embodiments identify inactive elements by examining incoming signals.

BACKGROUND

High-speed data communication systems are known to include current-modedriver amplifiers (drivers) and receivers. For best speed performance,the drive current should be calibrated. Such calibration should accountfor process variations, and is preferably repeated as needed tocompensate for changes due to supply-voltage and temperaturefluctuations.

Supply-voltage and temperature fluctuations occur during deviceoperation, so driver recalibration is often desired of active(transmitting) drivers. Unfortunately, driver recalibration canintroduce noise, and so is typically carried out on inactive drivers.Recalibration schemes either interrupt transmission or await a time whenthe driver is inactive. A better solution would allow for recalibrationof active drivers without interrupting data transmission or introducingnoise.

BRIEF DESCRIPTION OF THE FIGURES

FIG. 1 is a block diagram of a data communication system 100 inaccordance with one embodiment.

FIG. 2 depicts an amplifier 200 in accordance with another embodiment.

FIG. 3 depicts impedance calibration circuitry 225 in accordance withone embodiment.

FIG. 4 depicts one of impedances 230 of FIG. 2 in accordance with oneembodiment.

FIG. 5 depicts a state machine 500 illustrating the function of updatelogic 220 in accordance with one embodiment.

FIG. 6 depicts an amplifier 600 with a conventional pull-up resistor 605and a pull-down driver 610 adapted in accordance with one embodiment.

FIG. 7 depicts a push-pull amplifier 700 in accordance with anotherembodiment.

FIG. 8 depicts an amplifier 800 in accordance with an embodiment thatincludes push-pull amplifier 700 of FIG. 7 and, to update the driverswithin amplifier 700, some update control circuitry 805 and a drivercalibration block 810.

FIG. 9 depicts a driver 900 that can be used in place of each driver ofFIG. 8.

FIG. 10 depicts calibration circuitry 815 of FIG. 8 in accordance withone embodiment.

FIG. 11 depicts a communication system 1100 in accordance with anotherembodiment.

FIG. 12 depicts driver circuitry 1200 in accordance with anotherembodiment.

DETAILED DESCRIPTION

FIG. 1 is a block diagram of a data communication system 100 inaccordance with one embodiment. Communication system 100 includes atransmitting amplifier 105 connected to a receiver 110 via acommunication channel 115. Amplifier 105 includes a pull-down driver120, the drive strength of which is calibrated by some drivercalibration circuitry 125. Changing drive strength while driver 120 isin a low-impedance state can introduce undesirable glitches in thetransmitted signal. To prevent such glitches, update logic 130 monitorsincoming data Din on the corresponding input node to identify timesduring which driver 120 is inactive is in a high-impedance state andonly then enables driver calibration circuitry 125 to recalibrate thedrive strength of driver 120. Amplifier 105 can thus periodically adjustthe drive strength of driver 120 to compensate for temperature andsupply-voltage fluctuations without interrupting the transmission ofdata. As with other designations herein, each of Din, Dtx and Drx referboth to a signal and a corresponding node; whether a given designationrefers to a signal or a node will be clear from the context.

FIG. 2 depicts an amplifier 200 in accordance with another embodiment.The drive circuitry of amplifier 200 is instantiated on anintegrated-circuit (IC) die 205 coupled to a reference voltage Vref viaan external reference resistor Rref. The amplifier conveys data from aninput node D0 to the control terminals of a pull-up driver 210 and apull-down driver 215, which are coupled to the input node via a pair ofsequential storage elements 211 and 213. Drivers 210 and 215 extendbetween an amplifier output node Dtx and respective supply terminals Vioand ground. While there may be some cross-over, in general one ofdrivers 210 and 215 is active and the other inactive when transmittingdata on output node Dtx. Amplifier 200 includes update logic 220 thatmonitors incoming data to schedule adjustments for the inactive driver.These adjustments are based upon calibration signals developed by someimpedance calibration circuitry 225 coupled to the calibration ports ofdrivers 210 and 215.

Drivers 210 and 215 can be implemented in a number of configurations. Inthis example, each driver includes an adjustable impedance 230 coupledin series with a transistor between output node Dtx and the respectivesupply terminal. Each impedance 230 includes an enable port coupled toenable logic 220 and a calibration port Cal[0:4] coupled to impedancecalibration circuitry 225. Update logic monitors two consecutive bits D0and D1 of the incoming signal to identifying timing windows during whichone of drivers 210 and 215 will be inactive, and then enables therespective impedance 230 of the inactive driver to receive thecalibration signal Cal[0:4]. Update logic 220 uses two incoming bits toidentify inactive drivers, but can use more or fewer bits in otherembodiments. Update logic 220, impedance calibration circuitry, or bothcan also be enabled periodically in still other embodiments.

FIG. 3 depicts impedance calibration circuitry 225 in accordance withone embodiment. Calibration circuitry 225 includes a current source 300that draws identical currents Irr through reference resistor Rref and acalibration impedance 305. The impedance through impedance 305 changesin response to calibration signal Cal[0:4] in a manner proportional toimpedances 230 of FIG. 2, the proportion being one-to-one in someembodiments. A comparator 310 compares the voltage Vrr from referenceresistor Rref with the voltage Vcal from impedance 305, causing acounter 315 to increment (decrement) when voltage Vrr is greater than(less than) calibration voltage Vcal. In this way, impedance calibrationcircuitry 225 maintains the proportion between impedance 305 andreference resistor Rref. Impedance 305 is similar to impedances 230, andso responds similarly to process, voltage, and temperature variations.The calibration signal required to maintain the desired proportionalitybetween impedance 305 and reference resistor Rref can therefore bedistributed to impedances 230 to similarly maintain their values.

FIG. 4 depicts one of impedances 230 of FIG. 2 in accordance with oneembodiment. Impedance 230 includes a plurality of transistors 400coupled between a pair of current-handling terminals T1 and T2.Transistors 400 are, in this example, coupled in parallel. The gatewidths of transistors 400 are binary weighted to provide a range of 2⁵impedance values. The contents of five storage elements 405 determinewhich of transistors 400 is biased on. Each storage element 405 includesa enable terminal that allows update logic 220 of FIG. 2 to selectivelydirect calibration updates to inactive drivers. In one embodiment,calibration impedance 305 of FIG. 3 is identical to impedance 230,absent storage elements 405 and the associated enable terminal En#.

FIG. 5 depicts a state machine 500 illustrating the function of updatelogic 220 in accordance with one embodiment. Beginning in state 00, bothenable signals En1 and En2 are at voltages expressing a logic zero. Inthat case, the storage elements within both impedances 230 are unable tocapture updated calibration signals. Update logic 220 remains instate 00until the incoming data symbols D0 and D1 are both ones or both zeros,in which case a sufficiently long update window exists for the one ofimpedances 230 not used to expresses the consecutive symbols. Assume,for example, that data bits D0 and D1 are both logic ones: in that case,update logic 220 transitions to state 10 on the next transmit clock edgeand asserts enable signal En1. Impedance 230 within pull-up driver 210then captures the current calibration signal Cal[0:4] on the nexttransmit clock edge, and is thus recalibrated. Update logic 220 remainsin state 10 until data D0 is a zero, and then transitions back to state00. Update logic 220 similarly updates pull-down driver 215, moving tostate 01 when data symbols D0 and D1 are both zeros and back to state 00when symbol D0 returns to a logic one.

FIG. 6 depicts an amplifier 600 with a conventional pull-up resistor 605and a pull-down driver 610 adapted in accordance with one embodiment.Unlike the embodiments noted above, driver 610 is divided into aplurality (e.g. four) of drivers Dvr[0:3] coupled in parallel betweenoutput node Dtx and one supply terminal (ground). Incoming data Din andcalibration signal Cal[0:4] are fed to each of drivers Dvr[0:3]. Acollection of enable signals En[0:3], each coupled to an enable port ofa respective one of drivers Dvr[0:3], allows external control circuitryto selectively enable the calibration feature of each driver.

Driver 610 can be adapted to support a number of calibration schemesthat may or may not take into consideration the pattern of the incomingdata. In one embodiment, for example, only three of the four driversDvr[0:3] are enabled at any one time, leaving the fourth to receiveupdated calibration signals Cal[0:4] without producing a glitch in theoutgoing data. The newly calibrated driver can then substitute for oneof the active drivers, at which time newly inactive driver is availablefor calibration. In this way, all the active drivers can be successivelyupdated. In another embodiment all of the drivers may be activesimultaneously, but the calibration port of only one or a subset isenabled at a time. In either case, driver 610 may be updated bysuccessively updating less than all of drivers Dvr[0:3].

FIG. 7 depicts a push-pull amplifier 700 in accordance with anotherembodiment. Amplifier 700 is similar to amplifier 600 of FIG. 6, butuses calibrated pull-up drivers in place of resistor 605. Amplifier 700is divided into a plurality of (e.g. four) drivers Ddvr[0:3] coupled inparallel between supply terminals Vio and ground. Data Dp/Dn andcalibration signals Pcal[0:4] and Ncal[0:4] are fed to each of driversDdvr[0:3]. A collection of enable signals En[0:3], each coupled to anenable port of a respective one of drivers Ddvr[0:3], allows externalcontrol circuitry to selectively enable the calibration feature of eachdriver. Exemplary control circuitry is detailed below in connection withFIG. 8.

Each of drivers Ddvr[0:3] includes a pull-up driver and a pull-downdriver. Driver Ddvr0, for example, includes a pull-up driver pDvr0 and apull-down driver nDvr0. The pull-up drivers are activated by data signalDp and are calibrated using calibration signals Pcal[0:4], whereas thepull-down drivers are activated by data signal Dn and are calibratedusing calibration signals Ncal[0:4]. As with amplifier 600 of FIG. 6,amplifier 700 can be adapted to support a number of calibration schemesthat may or may not take into consideration the pattern of the incomingdata.

FIG. 8 depicts an amplifier 800 in accordance with an embodiment thatincludes push-pull amplifier 700 of FIG. 7 and, to update the driverswithin amplifier 700, some update control circuitry 805 and acalibration control block 810. Calibration control block 810 includescalibration circuitry 815 that maintains impedance calibration signalsPcal[0:3] and Ncal[0:4] as needed to adjust the strengths of driversDdvr[0:3] to account for process, temperature, and supply voltagefluctuations. Calibration control block 810 additionally includes, foreach driver, a register 820 and a multiplexer 825 that together applydriver-specific calibration signals to the drivers and facilitatedriver-specific update control.

Update control circuitry 805 includes a state machine 830, an associatedprogrammable counter 835, and a pair of shift registers 840 and 845.Update control circuitry 805 delivers update signals UD[0:3] tocalibration control block 810 to select which driver is to be updated,and delivers enable signals En[0:3], one to each driver, to selectivelyenable the drivers. Amplifier 800 may include one or more fixed oradjustable on-die termination elements Rodt. The operation of amplifier800 is described below in connection with the following Table 1.

TABLE 1 Clock Tick Number State Update En UD[0:3] Driver En EN[0:3] 0Idle 0000 1110 n Update 0001 1110 2n Switch 0001 0111 3n Update 10000111 4n Switch 1000 1011 5n Update 0100 1011 ∥ ∥ ∥ ∥

State machine 830 can be disabled by asserting a disable signal (Dis=1),in which case state machine 830 remains in an idle state. Shift register840 stores all zeroes in the Idle state, so the outputs of registers 820are fed back to their respective inputs via multiplexers 825, preventingcalibration updates to any of drivers Ddvr[0:3]. Shift register 845stores ones and a single zero (e.g. 1110) in the Idle state so that allbut one of the drivers are enabled. In the example of Table 1, theleast-significant bits of UD[0:3] and EN[0:3] correspond to driverDdvr0, so driver Ddvr0 is disabled.

State machine 830 enters the Update state when the disable signal isdeasserted (Dis=0). The disable signal might be deasserted periodically,after a number of clock cycles n dictated by programmable counter 835,for example. A single logic one is loaded into the location of shiftregister 840 corresponding to the disabled driver Ddvr0, gating theoutput of calibration circuitry 815 to the one of registers 820associated with driver Ddvr0. That register will therefore capture anychanges to calibration signals Pcal[0:4] and Ncal[0:4] on the next clockcycle, and will apply the updated signals to driver Ddvr0.

After again waiting n clock cycles, state machine 830 transitions tostate Switch. Shift register 845 shifts the stored zero one bit, thusenabling the recently updated driver Ddvr0 and disabling another (inthis case, driver Ddvr3). State machine 830 will continue to vacillatebetween the update and switch states until the disable signal isasserted (Dis=1).

In the embodiment of FIG. 8, one driver of amplifier 800 is alwaysinactive, and so can be calibrated without adversely impacting databeing transmitted. Other embodiments operate in a manner similar toamplifier 105 of FIG. 1 and amplifier 200 of FIG. 2, in which case theincoming data Dp/Dn is monitored to find update windows during whichpull-up or pull-down drivers within drivers Ddvr[0:3] are inactive.

Only four drivers are coupled in parallel in FIG. 8, though more orfewer may be used. In addition, the number of disabled drivers can bechanged to provide coarse adjustment to the overall driver strength. Thenumber of enabled drivers might be determined at start-up, for example,with shift registers 840 and 845 loaded with the appropriate numbers ofones and zeroes. The calibration process detailed above can then beapplied as needed to compensate for changes in temperature and supplyvoltage.

FIG. 9 depicts a driver 900 that can be used in place of each driver ofFIG. 8. Driver 900 includes a pull-up driver 905 and a pull-down driver910 coupled in series between first and second supply terminals Vio andground. The driver output Dtx is taken from the common node betweendrivers 905 and 910.

Driver 905 includes six PMOS transistors 915 coupled in parallel betweennodes Vio and Dtx, but there can be more or fewer, depending upon thedesired range and granularity of adjustment. Each PMOS transistorcontrols the current through a respective resistive path. Theseresistive paths can be binary-weighted, an area-efficient configurationthat produces a large number of potential impedance values. The I-Vcharacteristics of transistors may be somewhat non-linear, and thisnon-linearity may introduce some non-linearity in the impedance throughdriver 905. A resistor 925, e.g. of polysilicon, improves the linearityof the impedance through driver 905 over the range of interest. In anembodiment that complies with a stub series-terminated logic (SSTL)interface standard in which Vio may be 1.8 Volts, 2.5 Volts, or 3.3Volts, the impedances through drivers 905 and 910 can be adjusted over arange of 14-22 Ohms in steps of 0.5 Ohms.

The enable signal En# (e.g., En[0]) controls the topmost transistor 915via a two-input NAND gate 930 and the remaining transistors 915 viathree-input NAND gates 935: when enable En[#] is a zero, each of NANDgates 930 and 935 issues a logic one to the gates of transistors 915,turning them off. If the enable signal is a one, NAND gate 930 turns onthe topmost transistor 915 when data signal Dp is a logic one. Those ofNAND gates 935 receiving a logic one from the corresponding bit ofcalibration signal Pcal[0:4] will also enable their correspondingtransistors 915 when data signal Dp is a logic one. In the depictedembodiment, a series of buffers 940 delays input signal Dp so enabledtransistors 915 are turned on successively to control the slew rate ofdriver 900. Buffers 940 may exhibit fixed or adjustable delays.

In some embodiments, the core logic used to implement control logic,such as NAND gates 930 and 935, is powered using a supply-voltage levellower than the input/output voltage Vio. Level shifters may therefore beincluded as need to communicate logic signals between e.g. NAND gates930 and 935 and transistors 915. The placement and configuration oflevel shifters is well known to those of skill in the art, and istherefore omitted here for clarity of expression.

Pull-down driver 910 is similar to pull-up driver 905, but uses NMOStransistors in lieu of PMOS and AND gates in lieu of NAND gates. Adetailed discussion of driver 910 is omitted for brevity.

FIG. 10 depicts calibration circuitry 815 of FIG. 8 in accordance withone embodiment. Calibration circuitry 815 includes two n-type referenceimpedances 1005 and 1010 and one p-type reference impedance 1015. N-typereference impedances 1005 and 1010 are designed to be identical, ornearly so, to the transistors of pull-down driver 910 depicted in FIG.9, with the lowermost transistor biased on and the five remainingtransistors controlled by calibration signal Ncal[0:4]. The transistorsof driver 910 and reference impedances 1005 and 1010 are made using thesame process and are subject to similar fluctuations in supply voltageand temperature, and can therefore be expected to exhibit similarimpedances in response to the same calibration signal. P-type referenceimpedance 1015 is designed to be identical, or nearly so, to thetransistors of pull-up driver 905 of FIG. 9, with the uppermosttransistor biased on and the five remaining transistors controlled bycalibration signal Pcal[0:4]. The transistors of driver 905 andreference impedance 1015 are made using the same process and are subjectto similar fluctuations in supply voltage and temperature, and cantherefore be expected to exhibit similar impedances in response to thesame calibration signal.

Calibration circuitry 815 includes some control logic 1020, such as astate machine, that calibrates impedances 1005, 1010, and 1015 bycomparison with an external precision reference resistor Rref. To beginwith, control logic 1020 causes a multiplexer 1025 to convey acalibration voltage Vcal (e.g., half of Vio) to one terminal of acomparator 1030. The other input terminal of comparator 1030 is coupledbetween external reference resistor Rref and internal referenceimpedance 1005. A counter 1035 counts up when voltage Vrr from referenceresistor Rref exceeds the calibration voltage Vcal. The contents ofcounter 1035 is captured in a register 1040 during the pull-downcalibration, so that Ncal[0:4] increases with counter 1035. Theincreased count reduces the value of impedance 1005, and consequentlyreduces voltage Vrr. Voltage Vrr thus converges on voltage Vcal. In thecase in which voltage Vcal is half of voltage Vio, this convergenceoccurs when the value of impedance 1005 equals that of referenceresistor Rref. Impedances 1005 and 1010 are identical, so this procedurecalibrates them both.

Once impedances 1005 and 1010 have had sufficient time for calibration,control logic 1020 prevents further updates to register 1040, and thusholds the values of impedances 1005 and 1010. Control logic 1020 thencauses multiplexer 1025 to select the node between impedances 1015 and1010 for comparison to voltage Vrr and enables a second register 1045 toreceive the counts from counter 1035. Counter 1035 counts up when thevoltage Vrr exceeds the voltage between impedances 1010 and 1015. Thecontents of counter 1035 is captured in register 1045 during the pull-upcalibration, so that Pcal[0:4] increases with counter 1035. Theincreased count reduces the impedance through impedance 1015, andconsequently increases the voltage from multiplexer 1025. The twovoltages converge when the value of impedance 1015 equals that ofreference resistor Rref. Control logic 1020 then freezes the countwithin register 1045 until initiating the next calibration sequence.

FIG. 11 depicts a communication system 1100 in accordance with anotherembodiment. System 1100 is in many ways similar to system 100 of FIG. 1,like-identified elements being the same or similar. The operation ofsystem 1100 is sufficiently similar to system 100 that a detaileddiscussion is unnecessary, and is therefore omitted for brevity.

FIG. 12 depicts driver circuitry 1200 in accordance with anotherembodiment. Circuitry 1200 includes an amplifier 1205 and a pair oftermination elements 1210 and 1215. Amplifier 1205 can be adaptive, e.g.in the manner of amplifier 700 of FIG. 7. Termination element 1210includes a number (e.g. four) of sub-elements 1220, each of which may besimilar to driver 905 of FIG. 9 but omits data Dp as an input. Likewise,element 1215 includes a number (e.g. four) of sub-elements 1225, each ofwhich may be similar to driver 910 of FIG. 9 but omits data Dn as aninput. Sub-elements 1220 and 1225 can be adaptively calibrated in thesame manners as the drivers detailed above to facilitate ODT calibrationthat does not interfere or that interferes minimally with data transfer.Circuitry similar to calibration circuitry 815 of FIGS. 8 and 10 can beused to calibrate termination elements 1210 and 1215, though theimpedance and reference voltages may be changed as appropriate toestablish a desired termination impedance. Calibration circuitry 815 canbe modified to support the requisite termination-calibration impedancesand voltages such that the calibration sequences for the drivers andtermination elements share some of the calibration circuitry (e.g.,comparator 1030, counter 1035, and control logic 1020).

Each of the foregoing embodiments support drive calibration schemes thatdo not interrupt data transfer. Such schemes are useful whereuninterrupted transmission is important, and are not limited to data.Clock drivers, used for on-die buffering schemes for example, transmitrelatively continuous clock signals and might thus benefit from clockbuffers that can be recalibrated without interrupting clock signals.Embodiments that update active clock drivers may differ from those thatupdate active data drivers, however, because the signal pattern conveyedvia a clock driver—alternating high and low levels—is known in advance.Inactive pull-up or pull-down drivers of a clock buffer can thus beidentified without monitoring the incoming pattern. If, for example, thevoltage level transmitted by a clock buffer is low, update logic canassume the pull-up portion of the clock driver is inactive and that thepull-down portion will be inactive in the next clock cycle. The sameassumption can be made if the clock buffer transmitted a low voltagelevel an even number of clock cycles before or after the present clockcycle.

The amplifiers and receivers discussed herein may be instantiated onseparate integrated-circuit (IC) dies, each of which may be any ofmyriad types of processing chips capable of communicating electricalsignals. Typical examples include IC dies that communicate via parallelor serial bus interfaces. Communicating devices can use eitherunidirectional or bidirectional signal lines, as is well known to thoseof skill in the art. Further, while the depicted embodiment is describedin connection with a typical case in which two dies communicate signalsvia external lines, other embodiments calibrate drivers to improvecommunication speed between circuits that exist on the same die orbetween devices that communicate via a wireless channel.

An output of a process for designing an integrated circuit, or a portionof an integrated circuit, comprising one or more of the circuitsdescribed herein may be a computer-readable medium such as, for example,a magnetic tape or an optical or magnetic disk. The computer-readablemedium may be encoded with data structures or other informationdescribing circuitry that may be physically instantiated as anintegrated circuit or portion of an integrated circuit. Although variousformats may be used for such encoding, these data structures arecommonly written in Caltech Intermediate Format (CIF), Calma GDS IIStream Format (GDSII), or Electronic Design Interchange Format (EDIF).Those of skill in the art of integrated circuit design can develop suchdata structures from schematic diagrams of the type detailed above andthe corresponding descriptions and encode the data structures oncomputer readable medium. Those of skill in the art of integratedcircuit fabrication can use such encoded data to fabricate integratedcircuits comprising one or more of the circuits described herein.

While the present invention has been described in connection withspecific embodiments, variations of these embodiments will be obvious tothose of ordinary skill in the art. For example, (1) the externalvoltage and resistance references may be substituted in otherembodiments with on-chip references; (2) embodiments of the inventioncan be adapted for use with multi-PAM signals; (3) and clock drivers(either for internal use or transmitting via e.g. an output pad) usedfor e.g. on-die buffering schemes. Moreover, some components are showndirectly connected to one another while others are shown connected viaintermediate components. In each instance the method of interconnection,or “coupling,” establishes some desired electrical communication betweentwo or more circuit nodes, or terminals. Such coupling may often beaccomplished using a number of circuit configurations, as will beunderstood by those of skill in the art. Therefore, the spirit and scopeof the appended claims should not be limited to the foregoingdescription.

1. A method of driving a signal over a channel, the method comprising:a. monitoring the signal for first and second logic levels; b. pulling,in response to the first logic level, the channel toward a supplyvoltage at a first drive strength; C. adjusting, in response to thesecond logic level, the first drive strength to a second drive strength;and d. pulling, in response to the first logic level, the channel towardthe supply voltage at the second drive strength.
 2. The method of claim1, further comprising: a. pulling, in response to the second logiclevel, the communication channel toward a second supply voltage at athird drive strength; b. adjusting, in response to the first logiclevel, the third drive strength to a fourth drive strength; and c.pulling, in response to the second logic level, the communicationchannel toward the second supply voltage at the fourth drive strength.3. The method of claim 1, further comprising adjusting a drive impedanceto adjust the first drive strength.
 4. A computer-readable medium havingstored thereon a data structure defining an amplifier, the datastructure comprising: a. first data representing an input node, anoutput node, and a supply terminal; b. second data representing animpedance coupled between the supply terminal and the output node, thesecond data specifying the impedance as including a calibration port, anenable port, and a control terminal coupled to the input node; c.impedance calibration circuitry coupled to the calibration port; and d.update logic coupled between the input node and the enable port.
 5. Adriver comprising: a. an input node receiving an input signal, includingfirst and second logic levels; b. an output node; c. a supply terminal;d. a drive element coupled between the supply terminal and the outputnode, the drive element including a control terminal coupled to theinput node, wherein the drive element exhibits a first impedance in anactive state responsive to the first logic level and a second impedancein an inactive state responsive to the second logic level, the secondimpedance having a value higher than the first impedance; and e. meansfor adjusting the first impedance when the drive element is in theinactive state.
 6. An amplifier comprising: a. an input node; b. anoutput node; c. a supply terminal; d. a plurality of drive elementscoupled in parallel between the supply terminal and the output node,each of the drive elements including a calibration port, an enable port,and a control terminal coupled to the input node; and e. an impedancecalibration control block coupled to the calibration ports.
 7. Theamplifier of claim 6, the impedance calibration control block includingimpedance calibration circuitry selectively coupled to the calibrationports.
 8. The amplifier of claim 7, the impedance calibration controlblock including sequential storage elements coupled between theimpedance calibration circuitry and each of the calibration ports. 9.The amplifier of claim 7, further comprising update control circuitrycoupled to each of the enable ports.
 10. The amplifier of claim 9,wherein the update control circuitry selectively disables at least oneof the drive elements, leaving the remaining ones of the drive elementsenabled.
 11. The amplifier of claim 9, wherein the impedance calibrationcontrol block includes an update control port coupled to the updatecontrol circuitry, and wherein the update control circuitry selectivelycouples the impedance calibration circuitry to at least one of thecalibration ports.
 12. The amplifier of claim 6, wherein the impedancecalibration control block successively calibrates each of the driveelements.
 13. The amplifier of claim 12, further comprising updatecontrol circuitry that disables one of the drive elements while theimpedance calibration control block calibrates the disabled one of thedrive elements.
 14. The amplifier of claim 13, wherein the updatecontrol circuitry controls the impedance calibration control block todetermine which of the drive elements is calibrated.